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Chapter 4:
Bandpass Modulation and Demodulation
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| 4.5.4 Required Tone Spacing for Noncoherent
Orthogonal FSK Signaling
= FSK is usually implemented as orthogonal signaling, but not all FSK
signaling is orthogonal
= How can we tell
a Ifthe two tones f1 and f2 are orthogonal to each other
a Or they are uncorrelated over symbol time T
= Property: any pair of tones in the set must have a frequency
separation that is a multiple of 1/T Hz
=» A tone with frequency f1 that is switched on for a symbol duration T
seconds and then switched off can be analytically described as:
S,(t) = (cos(277,t) rect(t/T))
1 for-T/2<t<T/2
rect(t/T) =
rect I={) for |t|>T/2
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Example 4.3: Non-coherent FSK signaling
= Two waveforms for:cos(27 f+) and cos 2z f,t where f1>f2, the
symbol rate 1/T and = a constant arbitrary angle
(a) Prove that the minimum tone spacing for non coherently
detected orthogonal FSK signaling is 1/T
Tr
[cos(2z fr+)cos2xf,rdr=0 (eq 4.45)
0
T T
cos | cos 2z fit cos 2x f,tdt—sin pl sin2z ft cos2x ft di =0
0 0
cos #{[cos 2m(f, +f)t +cos2a(f, — f)tldt
-sing | [sin2x(f, +f,)t +sin27(f — f,)t]dt=0
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sg| meal + fi)t + sin2z(f,-f5 *)
aft Sr) If, F2) Io
T
1 sin gl 2a +h sett Lo)
2a fit hy) 2a(fi- fr)
0
cong| 2 +A , sin2zth =F)
2a(fith) orf fy)
sing) — —=
2m( firth) 2a(fi- fy)
Assume that f1+f2 >> 1
sin2a(f,+ fT __ cos 2a(f, +A )T <0
2m(fi+ fy) 2a(fit fr)
SOP SAT =}, S082RUL = TI 6
(eq 4.49)
(eq 4.50)
@
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Combining eq-4.49 & eq-4.50
cos gsin 27(f, — f,)T +sing[cos 2a(f, - f,)T -1] 0 (eq 4.51)
Note that for arbitrary ¢, the terms eq4.51can sum to 0 only when sin 27(f, — f,)T =0
and simultaneously cos 27(f, — f,)T =1
sinx=0 forx=nz and
cosx=1 for x =2ka wherenand k are integers
for arbitrary ¢:
2n(f,—f)P=2ke or f-f == (eq 4.52)
l.
f-h= F (minimum tone spacing at k =1)
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= Analytical expression can be written as
S(t)=A g(t)cos[a,t+é(O], O<rsT7,, i=1,2,....,M
where
a g(t) is signal pulse shape
a A=amplitude of the signal
a @=carrier phase
= The range of the carrier phase can be determined using
_ 2n(i-1)
9 (1) = ——
i=1,....M
grees
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=n Wecan now write the analytical expression as
s= Fs cos t+ +20) O<1<T,, and i=1,2,...M
r, M
LY a eeer phase changes
Constant envelope abruptly at the beginning of
each signal interval
180-phase 0-phase -90-phase
shift shift shift
PP
UNIV VV,
= In PSK the carrier phase changes abruptly at the ve beginning o of each
signal interval while the amplitude remains constant
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= We can also write a PSK signal as:
s(t) = “Eco 0 20D)
T M
2E 2r(i-1) . 2n(i-l) .
= |_| cos ——— cos@,f-—sin———sin__ @f
T M M
= Furthermore, s,(t) may be represented as a linear combination of
two orthogonal functions w,(t) and w(t) as follows
s,(t) = VE 008, - VE sin =) w(t)
Where
y(t) = = cos| and y,(t) = = sin{o
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M-ary PSK
= In MPSK, the phase of the carrier takes on one of M possible values
27 (i-1
0) =2 Daa,
= Thus, MPSK waveform is expressed as k ,
M=2 MPSK
s,(t) = 2k co out anti >| 2 BPSK
T 4 OPSK
onli -1 8 8— PSK
s(t) = g(0)603 0 + a 4 16 16 — PSK
= Each s/t) may be expanded in terms of two basis function ¥,(f) and
W,(t) defined as
2 2.
Wi(t)= 7 0s ot, Yo) = 7 ot,
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Quadrature PSK (QPSK)
= Two BPSK in phase quadrature
= QPSK (or 4PSK) is a modulation technique that transmits 2-bit of
information using 4 states of phases
= For example
Each symbol corresponds
to two bits
= General expression:
[2E, 2eG-1)]
S ops (t) = TO cos ar. + 7-9, l= 1,2,3,4 O<r< T,
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The signals are:
2E _ |2Es Ty
Sy = ar cos(w,t) sS= op coset +a) =~
S
S,= 2k, cos(@,f +7) =—- cos(@,1)
Ss s
2E 37 2E,
Ss, =,/— cos(a@,t + —) = |= sin(@.\1)
YT, 2 17
Sy) =+ Js cos@,t, o—shift of 0° and 180°
8,,()=+ = sin@,t, shift of 90° and 270°
Ss
E,.
= sin(@,t)
s
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= Interms of basis functions
W(t) = = cos2af.t and y,(t)= = sin 27f.t
we can write Sops,(t) as
Sorse (= NE cos] 20D (0 - JE, sin] 20D by cn}
= With this expression, the constellation diagram can easily be drawn
= For example:
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Coherent Detection
1. Coherent Detection of PSK
Coherent detection requires the phase information
=» Acoherent detector operates by mixing the incoming data signal
with a locally generated carrier reference and selecting the
difference component from the mixer output
tsT
I
NA
“ame LPF
cos(ar)
‘ aq)
7
> S(t)
AC
e08( uct)
a Multiplying r(t) by the receiver LO (say A cos(w,t)) yields a signal
with a baseband component plus a component at 2f,
a TheLPF eliminates the high frequency component
a The output of the LPF is sampled once per bit period
a The sampled value z(T) is applied to a decision rule
= Z(T) is called the decision statistic
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= Matched filter receiver
r(t) h(t) =s(F,,-1) TD | | si
Zoos filter pair i
cos(a, A cos(«, f}
a AMF pair such as the root raised cosine filter can thus be used to
shape the source and received baseband symbols
a Infact this is a very common approach in signal detection in most
bandpass data modems
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